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Power Switching Regulators
The MC34163 series are monolithic power switching regulators that contain the primary functions required for dc-to-dc converters. This series is specifically designed to be incorporated in step-up, step-down, and voltage-inverting applications with a minimum number of external components. These devices consist of two high gain voltage feedback comparators, temperature compensated reference, controlled duty cycle oscillator, driver with bootstrap capability for increased efficiency, and a high current output switch. Protective features consist of cycle-by-cycle current limiting, and internal thermal shutdown. Also included is a low voltage indicator output designed to interface with microprocessor based systems. These devices are contained in a 16 pin dual-in-line heat tab plastic package for improved thermal conduction. * Output Switch Current in Excess of 3.0 A
MC34163 MC33163
POWER SWITCHING REGULATORS
SEMICONDUCTOR TECHNICAL DATA
* * * * * * * * *
16 1
Operation from 2.5 V to 40 V Input Low Standby Current Precision 2% Reference Controlled Duty Cycle Oscillator Driver with Bootstrap Capability for Increased Efficiency Cycle-by-Cycle Current Limiting Internal Thermal Shutdown Protection Low Voltage Indicator Output for Direct Microprocessor Interface Heat Tab Power Package
P SUFFIX PLASTIC PACKAGE CASE 648C (DIP-16)
16 1
DW SUFFIX PLASTIC PACKAGE CASE 751G (SOP-16L)
Representative Block Diagram
Driver Collector
PIN CONNECTIONS
9 LVI Output Voltage Feedback 2 10 Voltage Feedback 1 Switch Collector 11 Gnd 5 Timing Capacitor 6 7 8 (Top View) Switch Emitter 15 Device 16 Bootstrap Input MC34163DW MC34163P MC33163DW MC33163P TA = - 40 to +85C 12 11 10 Switch Collector 1 2 3 4 16 Bootstrap Input 15 14 13 Gnd Switch Emitter
Ipk Sense
8
- +
ILimit
VCC Timing Capacitor
7 + 6 OSC
5 Gnd 4 Voltage Feedback 1 Voltage Feedback 2 LVI Output 3
Control Logic and Thermal Shutdown +
12 Gnd 13 14 VCC Ipk Sense
9 Driver Collector
2 LVI 1
+ + -
+ + -
VFB
ORDERING INFORMATION
Operating Temperature Range TA = 0 to +70C Package SOP-16L DIP-16 SOP-16L DIP-16
Rev 2
+ (Bottom View) This device contains 114 active transistors.
(c) Motorola, Inc. 1996
MOTOROLA ANALOG IC DEVICE DATA
1
MC34163 MC33163
MAXIMUM RATINGS
Rating Power Supply Voltage Switch Collector Voltage Range Switch Emitter Voltage Range Switch Collector to Emitter Voltage Switch Current (Note 1) Driver Collector Voltage Driver Collector Current Bootstrap Input Current Range (Note 1) Current Sense Input Voltage Range Feedback and Timing Capacitor Input Voltage Range Low Voltage Indicator Output Voltage Range Low Voltage Indicator Output Sink Current Thermal Characteristics P Suffix, Dual-In-Line Case 648C Thermal Resistance, Junction-to-Air Thermal Resistance, Junction-to-Case (Pins 4, 5, 12, 13) DW Suffix, Surface Mount Case 751G Thermal Resistance, Junction-to-Air Thermal Resistance, Junction-to-Case (Pins 4, 5, 12, 13) Operating Junction Temperature Operating Ambient Temperature (Note 3) MC34163 MC33163 Storage Temperature Range Symbol VCC VC(switch) VE(switch) VCE(switch) ISW VC(driver) IC(driver) IBS Value 40 -1.0 to + 40 - 2.0 to VC(switch) 40 3.4 -1.0 to +40 150 -100 to +100 Unit V V V V A V mA mA V V V mA C/W RJA RJC RJA RJC TJ TA 0 to +70 - 40 to + 85 Tstg - 65 to +150 C 80 15
VIpk (Sense) (VCC-7.0) to (VCC+1.0) Vin VC(LVI) IC(LVI) -1.0 to + 7.0 -1.0 to + 40 10
94 18 +150 C C
ELECTRICAL CHARACTERISTICS (VCC = 15 V, Pin 16 = VCC, CT = 620 pF, for typical values TA = 25C, for min/max values TA is
the operating ambient temperature range that applies (Note 3), unless otherwise noted.) Characteristic OSCILLATOR Frequency TA = 25C Total Variation over VCC = 2.5 V to 40 V, and Temperature Charge Current Discharge Current Charge to Discharge Current Ratio Sawtooth Peak Voltage Sawtooth Valley Voltage FEEDBACK COMPARATOR 1 Threshold Voltage TA = 25C Line Regulation (VCC = 2.5 V to 40 V, TA = 25C) Total Variation over Line, and Temperature Input Bias Current (VFB1 = 5.05 V) Vth(FB1) 4.9 - 4.85 IIB(FB1) - 5.05 0.008 - 100 5.2 0.03 5.25 200 V %/V V A fOSC 46 45 Ichg Idischg Ichg/Idischg VOSC(P) VOSC(V) - - 8.0 - - 50 - 225 25 9.0 1.25 0.55 54 55 - - 10 - - A A - V V kHz Symbol Min Typ Max Unit
NOTES: 1. Maximum package power dissipation limits must be observed. 2. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. 3. Tlow = 0C for MC34163 Thigh = + 70C for MC34163 = - 40C for MC33163 = + 85C for MC33163
2
MOTOROLA ANALOG IC DEVICE DATA
MC34163 MC33163
ELECTRICAL CHARACTERISTICS (continued) (VCC = 15 V, Pin 16 = VCC, CT = 620 pF, for typical values TA = 25C, for min/max
values TA is the operating ambient temperature range that applies (Note 3), unless otherwise noted.) Characteristic FEEDBACK COMPARATOR 2 Threshold Voltage TA = 25C Line Regulation (VCC = 2.5 V to 40 V, TA = 25C) Total Variation over Line, and Temperature Input Bias Current (VFB2 = 1.25 V) CURRENT LIMIT COMPARATOR Threshold Voltage TA = 25C Total Variation over VCC = 2.5 V to 40 V, and Temperature Input Bias Current (VIpk (Sense) = 15 V) DRIVER AND OUTPUT SWITCH (Note 2) Sink Saturation Voltage (ISW = 2.5 A, Pins 14, 15 grounded) Non-Darlington Connection (RPin 9 = 110 to VCC, ISW/IDRV 20) Darlington Connection (Pins 9, 10, 11 connected) Collector Off-State Leakage Current (VCE = 40 V) Bootstrap Input Current Source (VBS = VCC + 5.0 V) Bootstrap Input Zener Clamp Voltage (IZ = 25 mA) LOW VOLTAGE INDICATOR Input Threshold (VFB2 Increasing) Input Hysteresis (VFB2 Decreasing) Output Sink Saturation Voltage (Isink = 2.0 mA) Output Off-State Leakage Current (VOH = 15 V) TOTAL DEVICE Standby Supply Current (VCC = 2.5 V to 40 V, Pin 8 = VCC, Pins 6, 14, 15 = Gnd, remaining pins open) ICC - 6.0 10 mA Vth VH VOL(LVI) IOH 1.07 - - - 1.125 15 0.15 0.01 1.18 - 0.4 5.0 V mV V A VCE(sat) - - IC(off) Isource(DRV) VZ - 0.5 VCC + 6.0 0.6 1.0 0.02 2.0 VCC + 7.0 1.0 1.4 100 4.0 VCC + 9.0 A mA V V Vth(Ipk Sense) - 230 IIB(sense) - 250 - 1.0 - 270 20 A mV Vth(FB2) 1.225 - 1.213 IIB(FB2) - 0.4 1.25 0.008 - 0 1.275 0.03 1.287 0.4 V %/V V A Symbol Min Typ Max Unit
NOTES: 1. Maximum package power dissipation limits must be observed. 2. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. 3. Tlow = 0C for MC34163 Thigh = + 70C for MC34163 = - 40C for MC33163 = + 85C for MC33163
100
f OSC, OSCILLATOR FREQUENCY CHANGE (%)
t on -t off , OUTPUT SWITCH ON-OFF TIME ( s)
Figure 1. Output Switch On-Off Time versus Oscillator Timing Capacitor
VCC = 15 V TA = 25C 1) ton, RDT = 2) ton, RDT = 20 k 3) ton, toff, RDT = 10 k 4) toff, RDT = 20 k 5) toff, RDT =
Figure 2. Oscillator Frequency Change versus Temperature
2.0 VCC = 15 V CT = 620 pF 0
1 2 3 4 5
10
- 2.0
- 4.0
1.0 0.1
1.0 CT, OSCILLATOR TIMING CAPACITOR (nF)
10
- 6.0 - 55
- 25
0 25 50 75 TA, AMBIENT TEMPERATURE (C)
100
125
MOTOROLA ANALOG IC DEVICE DATA
3
MC34163 MC33163
V th(FB2), COMPARATOR 2 THRESHOLD VOLTAGE (mV)
Figure 3. Feedback Comparator 1 Input Bias Current versus Temperature
140 IIB , INPUT BIAS CURRENT ( A) VCC = 15 V VFB1 = 5.05 V 120
Figure 4. Feedback Comparator 2 Threshold Voltage versus Temperature
1300 1280 1260 1240 Vth Min = 1225 mV 1220 1200 - 55 VCC = 15 V Vth Max = 1275 mV
100
Vth Typ = 1250 mV
80
60 - 55
- 25
0 25 50 75 TA, AMBIENT TEMPERATURE (C)
100
125
- 25
0 25 50 75 TA, AMBIENT TEMPERATURE (C)
100
125
I source (DRV) , BOOTSTRAP INPUT CURRENT SOURCE (mA)
V Z, BOOTSTRAP INPUT ZENER CLAMP VOLTAGE (V)
Figure 5. Bootstrap Input Current Source versus Temperature
2.8 VCC = 15 V Pin 16 = VCC + 5.0 V
Figure 6. Bootstrap Input Zener Clamp Voltage versus Temperature
7.6 IZ = 25 mA 7.4
2.4
2.0
7.2
1.6
7.0
1.2 - 55
- 25
0 25 50 75 TA, AMBIENT TEMPERATURE (C)
100
125
6.8 - 55
- 25
0 25 50 75 TA, AMBIENT TEMPERATURE (C)
100
125
Figure 7. Output Switch Source Saturation versus Emitter Current
0 VCE (sat), SOURCE SATURATION (V) VCE (sat), SINK SATURATION (V) VCC - 0.4 - 0.8 -1.2 -1.6 - 2.0 Darlington Configuration Emitter Sourcing Current to Gnd Pins 7, 8, 10, 11 = VCC Pins 4, 5, 12, 13 = Gnd TA = 25C, (Note 2) 1.2 1.0 0.8 0.6 0.4 0.2 0
Figure 8. Output Switch Sink Saturation versus Collector Current
Darlington, Pins 9, 10, 11 Connected
Bootstrapped, Pin 16 = VCC + 5.0 V
Non-Bootstrapped, Pin 16 = VCC 0 0.8 2.4 1.6 IE, EMITTER CURRENT (A) 3.2
Grounded Emitter Configuration Collector Sinking Current From VCC Pins 7, 8 = VCC = 15 V Pins 4, 5, 12, 13, 14, 15 = Gnd TA = 25C, (Note 2) Saturated Switch, RPin9 = 110 to VCC Gnd 0 0.8 1.6 2.4 IC, COLLECTOR CURRENT (A) 3.2
4
MOTOROLA ANALOG IC DEVICE DATA
MC34163 MC33163
Figure 9. Output Switch Negative Emitter Voltage versus Temperature
0 Gnd V E , EMITTER VOLTAGE (V) - 0.4 - 0.8 - 1.2 - 1.6 - 2.0 - 55 IC = 10 mA VCC = 15 V Pins 7, 8, 9, 10, 16 = VCC Pins 4, 6 = Gnd Pin 14 Driven Negative - 25 0 25 50 75 TA, AMBIENT TEMPERATURE (C) 100 125 IC = 10 A
V OL (LVI) , OUTPUT SATURATION VOLTAGE (V)
Figure 10. Low Voltage Indicator Output Sink Saturation Voltage versus Sink Current
0.5 0.4 0.3 0.2 0.1 0 VCC = 5 V TA = 25C
0
2.0 4.0 6.0 Isink, OUTPUT SINK CURRENT (mA)
8.0
Figure 11. Current Limit Comparator Threshold Voltage versus Temperature
V th (Ipk Sense) , THRESHOLD VOLTAGE (mV) 254 IIB (Sense), INPUT BIAS CURRENT ( A) VCC = 15 V 1.6 1.4 1.2 1.0 0.8
Figure 12. Current Limit Comparator Input Bias Current versus Temperature
VCC = 15 V VIpk (Sense) = 15 V
252
250
248
246 - 55
- 25
0 25 50 75 TA, AMBIENT TEMPERATURE (C)
100
125
0.6 - 55
- 25
0 25 50 75 TA, AMBIENT TEMPERATURE (C)
100
125
Figure 13. Standby Supply Current versus Supply Voltage
8.0 I CC, SUPPLY CURRENT (mA) I CC, SUPPLY CURRENT (mA) 7.2
Figure 14. Standby Supply Current versus Temperature
VCC = 15 V Pins 7, 8, 16 = VCC Pins 4, 6, 14 = Gnd Remaining Pins Open
6.0
6.4
4.0 Pins 7, 8, 16 = VCC Pins 4, 6, 14 = Gnd Remaining Pins Open TA = 25C 0 10 20 30 VCC, SUPPLY VOLTAGE (V) 40
5.6
2.0
4.8
0
4.0 - 55
- 25
0 25 50 75 TA, AMBIENT TEMPERATURE (C)
100
125
MOTOROLA ANALOG IC DEVICE DATA
5
MC34163 MC33163
Figure 15. Minimum Operating Supply Voltage versus Temperature
3.0 2.6 2.2 1.8 1.4 1.0 - 55 Pin 16 Open CT = 620 pF Pins 7,8 = VCC Pins 4, 14 = Gnd Pin 9 = 1.0 k to 15 V Pin 10 = 100 to 15 V 100 R JA, THERMAL RESISTANCE 80 60 40 20 PD(max) for TA = 70C RJA
V CC(min) , MINIMUM OPERATING SUPPLY VOLTAGE (V)
Figure 16. P Suffix (DIP-16) Thermal Resistance and Maximum Power Dissipation versus P.C.B. Copper Length
Printed circuit board heatsink example
JUNCTION-TO-AIR (C/W)
L
2.0 oz Copper
4.0 3.0 2.0 1.0
L 3.0 mm Graphs represent symmetrical layout
Pin 16 = VCC
- 25
0
25
50
75
100
125
0
0
10
20
30
40
0 50
TA, AMBIENT TEMPERATURE (C)
L, LENGTH OF COPPER (mm)
Figure 17. DW Suffix (SOP-16L) Thermal Resistance and Maximum Power Dissipation versus P.C.B. Copper Length
PD(max) for TA = 50C PD, MAXIMUM POWER DISSIPATION (W) 100 R JA, THERMAL RESISTANCE 90 80 70 L 60 50 40 30 0 10 20 30 40 L, LENGTH OF COPPER (mm) RJA 2.8 2.4 2.0 1.6 1.2 0.8 0.4
JUNCTION-TO-AIR ( C/W)
Graph represents symmetrical layout 2.0 oz. Copper L
3.0 mm
0 50
6
MOTOROLA ANALOG IC DEVICE DATA
P D , MAXIMUM POWER DISSIPATION (W)
5.0
IIIIII IIIIII
III III III I IIIIIII II IIIIIII I III
MC34163 MC33163
Figure 18. Representative Block Diagram
Current Limit
Ipk Sense RSC VCC Timing Capacitor Shutdown CT RDT Gnd
8 7
0.25 V +
- +
9 10
Driver Collector
+ 6 5 Thermal 4 3 45 k 2 1 LVI
+ + - + + -
Switch Collector Oscillator R Q S Latch + Q1 Q2 60 13 14 Switch Emitter Feedback Comparator 2.0 mA + 7.0 V 16 Bootstrap Input 15
+ -
11 12 Gnd
Voltage Feedback 1 Voltage Feedback 2 LVI Output
+
1.25 V 15 k + 1.125 V (Bottom View)
= Sink Only Positive True Logic
Figure 19. Typical Operating Waveforms
1 Comparator Output 0 1.25 V Timing Capacitor CT 0.55 V 1 Oscillator Output 0 On Output Switch Off Nominal Output Voltage Level t 9t
Output Voltage
Startup
Quiescent Operation
MOTOROLA ANALOG IC DEVICE DATA
7
MC34163 MC33163
INTRODUCTION
The MC34163 series are monolithic power switching regulators optimized for dc-to-dc converter applications. The combination of features in this series enables the system designer to directly implement step-up, step-down, and voltage-inverting converters with a minimum number of external components. Potential applications include cost sensitive consumer products as well as equipment for the automotive, computer, and industrial markets. A Representative Block Diagram is shown in Figure 18. clamping CT to ground with an external NPN small-signal transistor. Feedback and Low Voltage Indicator Comparators Output voltage control is established by the Feedback comparator. The inverting input is internally biased at 1.25 V and is not pinned out. The converter output voltage is typically divided down with two external resistors and monitored by the high impedance noninverting input at Pin 2. The maximum input bias current is 0.4 A, which can cause an output voltage error that is equal to the product of the input bias current and the upper divider resistance value. For applications that require 5.0 V, the converter output can be directly connected to the noninverting input at Pin 3. The high impedance input, Pin 2, must be grounded to prevent noise pickup. The internal resistor divider is set for a nominal voltage of 5.05 V. The additional 50 mV compensates for a 1.0% voltage drop in the cable and connector from the converter output to the load. The Feedback comparator's output state is controlled by the highest voltage applied to either of the two noninverting inputs. The Low Voltage Indicator (LVI) comparator is designed for use as a reset controller in microprocessor-based systems. The inverting input is internally biased at 1.125 V, which sets the noninverting input thresholds to 90% of nominal. The LVI comparator has 15 mV of hysteresis to prevent erratic reset operation. The Open Collector output is capable of sinking in excess of 6.0 mA (see Figure 10). An external resistor (RLVI) and capacitor (CDLY) can be used to program a reset delay time (tDLY) by the formula shown below, where Vth(MPU) is the microprocessor reset input threshold. Refer to Figure 20. 1 Vth(MPU) 1- Vout
OPERATING DESCRIPTION
The MC34163 operates as a fixed on-time, variable off-time voltage mode ripple regulator. In general, this mode of operation is somewhat analogous to a capacitor charge pum p and doe s n o t re q u i re d o mi n a n t p ol e l oop compensation for converter stability. The Typical Operating Waveforms are shown in Figure 19. The output voltage waveform shown is for a step-down converter with the ripple and phasing exaggerated for clarity. During initial converter startup, the feedback comparator senses that the output voltage level is below nominal. This causes the output switch to turn on and off at a frequency and duty cycle controlled by the oscillator, thus pumping up the output filter capacitor. When the output voltage level reaches nominal, the feedback comparator sets the latch, immediately terminating switch conduction. The feedback comparator will inhibit the switch until the load current causes the output voltage to fall below nominal. Under these conditions, output switch conduction can be inhibited for a partial oscillator cycle, a partial cycle plus a complete cycle, multiple cycles, or a partial cycle plus multiple cycles. Oscillator The oscillator frequency and on-time of the output switch are programmed by the value selected for timing capacitor CT. Capacitor CT is charged and discharged by a 9 to 1 ratio internal current source and sink, generating a negative going sawtooth waveform at Pin 6. As CT charges, an internal pulse is generated at the oscillator output. This pulse is connected to the NOR gate center input, preventing output switch conduction, and to the AND gate upper input, allowing the latch to be reset if the comparator output is low. Thus, the output switch is always disabled during ramp-up and can be enabled by the comparator output only at the start of ramp-down. The oscillator peak and valley thresholds are 1.25 V and 0.55 V, respectively, with a charge current of 225 A and a discharge current of 25 A, yielding a maximum on-time duty cycle of 90%. A reduction of the maximum duty cycle may be required for specific converter configurations. This can be accomplished with the addition of an external deadtime resistor (RDT) placed across CT. The resistor increases the discharge current which reduces the on-time of the output switch. A graph of the Output Switch On-Off Time versus Oscillator Timing Capacitance for various values of RDT is shown in Figure 1. Note that the maximum output duty cycle, ton/ton + toff, remains constant for values of CT greater than 0.2 nF. The converter output can be inhibited by
tDLY = RLVI CDLY In
Current Limit Comparator, Latch and Thermal Shutdown With a voltage mode ripple converter operating under normal conditions, output switch conduction is initiated by the oscillator and terminated by the Voltage Feedback comparator. Abnormal operating conditions occur when the converter output is overloaded or when feedback voltage sensing is lost. Under these conditions, the Current Limit comparator will protect the Output Switch. The switch current is converted to a voltage by inserting a fractional ohm resistor, RSC, in series with VCC and output switch transistor Q2. The voltage drop across RSC is monitored by the Current Sense comparator. If the voltage drop exceeds 250 mV with respect to VCC, the comparator will set the latch and terminate output switch conduction on a cycle-by-cycle basis. This Comparator/Latch configuration ensures that the Output Switch has only a single on-time during a given oscillator cycle. The calculation for a value of RSC is: RSC
+ Ipk0.25 V (Switch)
8
MOTOROLA ANALOG IC DEVICE DATA
MC34163 MC33163
Figures 11 and 12 show that the Current Sense comparator threshold is tightly controlled over temperature and has a typical input bias current of 1.0 A. The propagation delay from the comparator input to the Output Switch is typically 200 ns. The parasitic inductance associated with RSC and the circuit layout should be minimized. This will prevent unwanted voltage spikes that may falsely trip the Current Limit comparator. Internal thermal shutdown circuitry is provided to protect the IC in the event that the maximum junction temperature is exceeded. When activated, typically at 170C, the Latch is forced into the "Set" state, disabling the Output Switch. This feature is provided to prevent catastrophic failures from accidental device overheating. It is not intended to be used as a replacement for proper heatsinking. Driver and Output Switch To aid in system design flexibility and conversion efficiency, the driver current source and collector, and output switch collector and emitter are pinned out separately. This allows the designer the option of driving the output switch into saturation with a selected force gain or driving it near saturation when connected as a Darlington. The output switch has a typical current gain of 70 at 2.5 A and is designed to switch a maximum of 40 V collector to emitter, with up to 3.4 A peak collector current. The minimum value for RSC is: RSC(min) converter applications. This input is connected through a series resistor and capacitor to the switch emitter and is used to raise the internal 2.0 mA bias current source above VCC. An internal zener limits the bootstrap input voltage to VCC +7.0 V. The capacitor's equivalent series resistance must limit the zener current to less than 100 mA. An additional series resistor may be required when using tantalum or other low ESR capacitors. The equation below is used to calculate a minimum value bootstrap capacitor based on a minimum zener voltage and an upper limit current source. C B(min) t + I V + 4.0 mA ton 4.0 V
+ 0.001 ton
Parametric operation of the MC34163 is guaranteed over a supply voltage range of 2.5 V to 40 V. When operating below 3.0 V, the Bootstrap Input should be connected to VCC. Figure 15 shows that functional operation down to 1.7 V at room temperature is possible. Package The MC34163 is contained in a heatsinkable 16-lead plastic dual-in-line package in which the die is mounted on a special heat tab copper alloy lead frame. This tab consists of the four center ground pins that are specifically designed to improve thermal conduction from the die to the circuit board. Figures 16 and 17 show a simple and effective method of utilizing the printed circuit board medium as a heat dissipater by soldering these pins to an adequate area of copper foil. This permits the use of standard layout and mounting practices while having the ability to halve the junction-to-air thermal resistance. These examples are for a symmetrical layout on a single-sided board with two ounce per square foot of copper.
+
0.25 V 3.4 A
+
0.0735
When configured for step-down or voltage-inverting applications, as in Figures 20 and 24, the inductor will forward bias the output rectifier when the switch turns off. Rectifiers with a high forward voltage drop or long turn-on delay time should not be used. If the emitter is allowed to go sufficiently negative, collector current will flow, causing additional device heating and reduced conversion efficiency. Figure 9 shows that by clamping the emitter to 0.5 V, the collector current will be in the range 10 A over temperature. A 1N5822 or equivalent Schottky barrier rectifier is recommended to fulfill these requirements. A bootstrap input is provided to reduce the output switch saturation voltage in step-down and voltage-inverting
APPLICATIONS
The following converter applications show the simplicity and flexibility of this circuit architecture. Three main converter topologies are demonstrated with actual test data shown below each of the circuit diagrams.
MOTOROLA ANALOG IC DEVICE DATA
9
MC34163 MC33163
Figure 20. Step-Down Converter
0.25 V + Current Limit
8 Vin 12 V RSC 0.075 Cin 330 CT 680 pF + 7 + 6 5
- +
9 10
Oscillator R Q S Latch +
Q1 Q2 60
11 12 13 14
Thermal 4 3 45 k 2 Low Voltage Indicator Output RLVI 10 k CDLY 1 LVI
+ + - + + -
+
Feedback Comparator 2.0 mA
15 16
1N5822 0.02 CB RB 2200 180 H Coilcraft LO451-A Vout + 5.05 V/3.0 A CO
1.25 V 15 k + 1.125 V
+
7.0 V
L
(Bottom View)
Test Line Regulation Load Regulation Output Ripple Short Circuit Current Efficiency, Without Bootstrap Efficiency, With Bootstrap
Condition Vin = 8.0 V to 24 V, IO = 3.0 A Vin = 12 V, IO = 0.6 A to 3.0 A Vin = 12 V, IO = 3.0 A Vin = 12 V, RL = 0.1 Vin = 12 V, IO = 3.0 A Vin = 12 V, IO = 3.0 A
Results 6.0 mV = 0.06% 2.0 mV = 0.02% 36 mVpp 3.3 A 76.7% 81.2%
Figure 21. External Current Boost Connections for Ipk (Switch) Greater Than 3.4 A Figure 21A. External NPN Switch Figure 21B. External PNP Saturated Switch
8 7 + 6 5 4 3 2 1 + (Bottom View) + Q1 Q2
9 10 11 12 13 14 15 16 Q3
8 7 + 6 5 4 3 2 1 + (Bottom View) + Q1 Q2
9 10 11 12 13 14 15 16
Q3
10
MOTOROLA ANALOG IC DEVICE DATA
MC34163 MC33163
Figure 22. Step-Up Converter
0.25 V + Current Limit L 9 10 + 6 CT 680 pF 5 Thermal 4 3 45 k 2 Low Voltage Indicator Output 1 RLVI 1.0 k R2 47 k LVI
+ + - + + -
8 Vin 12 V RSC 0.075 Cin 330 + 7
- +
180 H Coilcraft LO451-A
Oscillator R Q S Latch +
Q1 Q2 60
11 12 13 1N5822 14
+
Feedback Comparator 2.0 mA 7.0 V
15 16
1.25 V 15 k + 1.125 V
+
R1 2.2 k
(Bottom View)
+C O 330
Vout 28 V/600 mA
Test Line Regulation Load Regulation Output Ripple Efficiency
Condition Vin = 9.0 V to 16 V, IO = 0.6 A Vin = 12 V, IO = 0.1 A to 0.6 A Vin = 12 V, IO = 0.6 A Vin = 12 V, IO = 0.6 A
Results 30 mV = 0.05% 50 mV = 0.09% 140 mVpp 88.1%
Figure 23. External Current Boost Connections for Ipk (Switch) Greater Than 3.4 A Figure 23A. External NPN Switch Figure 23B. External PNP Saturated Switch
8 7 + 6 5 4 3 2 1 + (Bottom View) + Q1 Q2
9 10 11 12 13 14 15 16 Q3
8 7 + 6 5 4 3 2 1 + (Bottom View) + Q1 Q2
9 10 11 12 13 14 15 16 Q3
MOTOROLA ANALOG IC DEVICE DATA
11
MC34163 MC33163
Figure 24. Voltage-Inverting Converter
0.25 V + Current Limit
8 Vin 12 V CT 470 pF RSC 0.075 Cin 330 + 7
- +
9 10
+ 6 5 Thermal 4 + 3 45 k 2 1 LVI
+ + - + + -
Oscillator R Q S Latch
Q1 Q2 60
11 12 13 Coilcraft LO451-A 14 L 180 H RB CB 1N5822 2200 + CO Vout - 12 V/1.0 A
+
Feedback Comparator 2.0 mA + 7.0 V
15 0.02 16
1.25 V 15 k + 1.125 V
R2 8.2 k
R1 953
(Bottom View)
Test Line Regulation Load Regulation Output Ripple Short Circuit Current Efficiency, Without Bootstrap Efficiency, With Bootstrap
Condition Vin = 9.0 V to 16 V, IO = 1.0 A Vin = 12 V, IO = 0.6 A to 1.0 A Vin = 12 V, IO = 1.0 A Vin = 12 V, RL = 0.1 Vin = 12 V, IO = 1.0 A Vin = 12 V, IO = 1.0 A
Results 5.0 mV = 0.02% 2.0 mV = 0.01% 130 mVpp 3.2 A 73.1% 77.5%
Figure 25. External Current Boost Connections for Ipk (Switch) Greater Than 3.4 A Figure 25A. External NPN Switch Figure 25B. External PNP Saturated Switch
8 7 6 5 4 3 2 1 + (Bottom View) +
9 10 Q1 Q2 11 12 13 14 15 16 Q3
8 7 + 6 5 4 3 2 1 + (Bottom View) + Q1 Q2
9 10 11 12 13 14 15 16
Q3
+
12
MOTOROLA ANALOG IC DEVICE DATA
MC34163 MC33163
Figure 26. Printed Circuit Board and Component Layout (Circuits of Figures 20, 22, 24)
+ + + +
+ VO -
R LVI CO
MC34163 Step-Down
+
-
CB
V in
R2
+
RB
C in
R1
+
+ + +
CT
R SC
L
+
Bottom View
Top View
+
+
+
+
+ MC34163 Step-Up
R LVI
VO
-
CO
+
V in
-
R2
+
R1
C in
CT
+
+ + +
R SC
L
+
Bottom View
Top View
+
+
+
MC34163 Voltage-Inverting
+
VO
+
-
CO
R1
+
-
CB
V in
R2
C in
RB
+
+
+ +
CT
+
R SC
L
+
Bottom View
Top View
All printed circuit boards are 2.58" in width by 1.9" in height.
MOTOROLA ANALOG IC DEVICE DATA
13
MC34163 MC33163
Figure 27. Design Equations
Calculation ton toff (Notes 1, 2, 3) Step-Down Step-Up V out Voltage-Inverting |V out|
) VF V in * V sat * V out
Vout t on t off
) VF - Vin
t on t off
V in - Vsat
) VF Vin * V sat
t on t off
ton
t on t off
)1
t on t off
)1 )1
t on t off
)1 )1
CT IL(avg) Ipk (Switch) RSC V in
32.143 * 10-6 Iout
32.143 * 10-6 I out ton toff
32.143 * 10-6 I out ton toff
IL(avg)
) DIL 2
IL(avg)
) DIL 2
IL(avg)
) DIL 2
0.25 Ipk (Switch)
0.25 Ipk (Switch) t on V in
0.25 Ipk (Switch) t on V in
L
* Vsat * Vout
DIL
1 8 CO V ref 2
* Vsat
DIL
* Vsat
DIL
O
t on
Vripple(pp)
DIL
) (ESR)2 )1
[ ton Iout C
O V ref R2 R1
[ ton Iout C
V ref R2 R1
Vout
R2 R1
)1
)1
The following Converter Characteristics must be chosen: Nominal operating input voltage. Desired output voltage. Desired output current. Desired peak-to-peak inductor ripple current. For maximum output current it is suggested that IL be chosen to be less than 10% of the average inductor current IL(avg). This will help prevent Ipk (Switch) from reaching the current limit threshold set by RSC. If the design goal is to use a minimum inductance value, let IL = 2(IL(avg)). This will proportionally reduce converter output current capability. p - Maximum output switch frequency. Vripple(pp) - Desired peak-to-peak output ripple voltage. For best performance the ripple voltage should be kept to a low value since it will directly affect line and load regulation. Capacitor CO should be a low equivalent series resistance (ESR) electrolytic designed for switching regulator applications. Vin - Vout - Iout - IL - NOTES: NOTES: NOTES: NOTES: 1. 2. 3. 3. Vsat - Saturation voltage of the output switch, refer to Figures 7 and 8. VF - Output rectifier forward voltage drop. Typical value for 1N5822 Schottky barrier rectifier is 0.5 V. The calculated ton/toff must not exceed the minimum guaranteed oscillator charge to discharge ratio of 8, at the minimum operating input voltage.
14
MOTOROLA ANALOG IC DEVICE DATA
MC34163 MC33163
OUTLINE DIMENSIONS
P SUFFIX PLASTIC PACKAGE CASE 648C-03 (DIP-16) -A-
16 9 NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. DIMENSION L TO CENTER OF LEADS WHEN FORMED PARALLEL. 4. DIMENSION B DOES NOT INCLUDE MOLD FLASH. 5. INTERNAL LEAD CONNECTION, BETWEEN 4 AND 5, 12 AND 13. INCHES MIN MAX 0.740 0.840 0.240 0.260 0.145 0.185 0.015 0.021 0.050 BSC 0.040 0.070 0.100 BSC 0.008 0.015 0.115 0.135 0.300 BSC 0 10 0.015 0.040 MILLIMETERS MIN MAX 18.80 21.34 6.10 6.60 3.69 4.69 0.38 0.53 1.27 BSC 1.02 1.78 2.54 BSC 0.20 0.38 2.92 3.43 7.62 BSC 0 10 0.39 1.01
-B-
1 8
L
NOTE 5
C -T-
SEATING PLANE
N F E G D 16 PL 0.13 (0.005)
M
M K J 16 PL 0.13 (0.005)
M
TB
S
T
A
S
DIM A B C D E F G J K L M N
DW SUFFIX PLASTIC PACKAGE CASE 751G-02 (SOP-16L) -A-
16 9 NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.13 (0.005) TOTAL IN EXCESS OF D DIMENSION AT MAXIMUM MATERIAL CONDITION. DIM A B C D F G J K M P R MILLIMETERS MIN MAX 10.15 10.45 7.60 7.40 2.65 2.35 0.49 0.35 0.90 0.50 1.27 BSC 0.32 0.25 0.25 0.10 7 0 10.05 10.55 0.25 0.75 INCHES MIN MAX 0.400 0.411 0.292 0.299 0.093 0.104 0.014 0.019 0.020 0.035 0.050 BSC 0.010 0.012 0.004 0.009 0 7 0.395 0.415 0.010 0.029
-B- P 8 PL 0.25 (0.010)
1 8 M
B
M
G 14 PL
J
F R X 45 C -T- D 16 PL 0.25 (0.010) K
M SEATING PLANE S
M
S
TA
B
MOTOROLA ANALOG IC DEVICE DATA
15
MC34163 MC33163
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. "Typical" parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer. Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution; P.O. Box 5405, Denver, Colorado 80217. 303-675-2140 or 1-800-441-2447 JAPAN: Nippon Motorola Ltd.: SPD, Strategic Planning Office, 4-32-1, Nishi-Gotanda, Shinagawa-ku, Tokyo 141, Japan. 81-3-5487-8488
MfaxTM: RMFAX0@email.sps.mot.com - TOUCHTONE 602-244-6609 ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park, - US & Canada ONLY 1-800-774-1848 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852-26629298 INTERNET: http://motorola.com/sps
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MC34163/D MOTOROLA ANALOG IC DEVICE DATA

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